Microwave network analysis

02/23/07 The Scattering Matrix 723 6/13 Note that if the ports are terminated in a matched load i.e., 0 L Z = Z , then Γ =nL 0 and therefore: Vn+ zn = 0 In other words, terminating a p

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3/4/2009 4_3 The Scattering Matrix 1/3

4.3 – The Scattering Matrix

Reading Assignment: pp 174-183

Admittance and Impedance matrices use the quantities I (z),

V (z), and Z (z) (or Y (z))

Q: Is there an equivalent matrix for transmission line

activity expressed in terms of V z+( ), V z−( ), and Γ( )z ?

A: Yes! Its called the scattering matrix

HO: T HE S CATTERING M ATRIX

Q: Can we likewise determine something physical about our device or network by simply looking at its scattering matrix?

A: HO: M ATCHED , R ECIPROCAL , L OSSLESS

E XAMPLE : A L OSSLESS , R ECIPROCAL D EVICE

Q: Isn’t all this linear algebra a bit academic? I mean, it

can’t help us design components, can it?

A: It sure can! An analysis of the scattering matrix can tell

us if a certain device is even possible to construct, and if so, what the form of the device must be

HO: T HE M ATCHED , L OSSLESS , R ECIPROCAL 3- PORT N ETWORK

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HO: T HE M ATCHED , L OSSLESS , R ECIPROCAL 4- PORT N ETWORK

Q: But how are scattering parameters useful? How do we use them to solve or analyze real microwave circuit problems?

A: Study the examples provided below!

E XAMPLE : T HE S CATTERING M ATRIX

E XAMPLE : S CATTERING P ARAMETERS

Q: OK, but how can we determine the scattering matrix of a

device?

A: We must carefully apply our transmission line theory!

E XAMPLE : D ETERMINING THE S CATTERING M ATRIX

Q: Determining the Scattering Matrix of a multi-port device would seem to be particularly laborious Is there any way to simplify the process?

A: Many (if not most) of the useful devices made by us

humans exhibit a high degree of symmetry This can greatly

simplify circuit analysis—if we know how to exploit it!

HO: C IRCUIT S YMMETRY

E XAMPLE : U SING S YMMETRY TO D ETERMINING A S CATTERING

M ATRIX

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Q: Is there any other way to use circuit symmetry to our

advantage?

A: Absolutely! One of the most powerful tools in circuit

analysis is Odd-Even Mode analysis

HO: S YMMETRIC C IRCUIT A NALYSIS

HO: O DD -E VEN M ODE A NALYSIS

E XAMPLE : O DD -E VEN M ODE C IRCUIT A NALYSIS

Q: Aren’t you finished with this section yet?

A: Just one more very important thing

HO: G ENERALIZED S CATTERING P ARAMETERS

E XAMPLE : T HE S CATTERING M ATRIX OF A C ONNECTOR

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02/23/07 The Scattering Matrix 723 1/13

The Scattering Matrix

At “low” frequencies, we can completely characterize a linear device or network using an impedance matrix, which relates the currents and voltages at each device terminal to the currents and voltages at all other terminals

But, at microwave frequencies, it

is difficult to measure total

currents and voltages!

* Instead, we can measure the magnitude and phase of each of the two transmission line waves ( ) and V z+ V z−( )

* In other words, we can determine the relationship

between the incident and reflected wave at each device terminal to the incident and reflected waves at all other

terminals

These relationships are completely represented by the

scattering matrix It completely describes the behavior of a linear, multi-port device at a given frequency ω , and a given line impedance Z0

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Consider now the 4-port microwave device shown below:

Note that we have now characterized transmission line activity

in terms of incident and “reflected” waves Note the negative

going “reflected” waves can be viewed as the waves exiting the

multi-port network or device

Æ Viewing transmission line activity this way, we can fully

characterize a multi-port device by its scattering parameters!

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Say there exists an incident wave on port 1 (i.e., V z1+ ( )1 ≠ 0),

while the incident waves on all other ports are known to be zero

(i.e., V z2+ ( )2 =V z3+( )3 =V z4+( )4 = 0)

Say we measure/determine the

voltage of the wave flowing into

port 1, at the port 1 plane (i.e.,

determine V z1+( 1 =z1P ))

Say we then measure/determine

the voltage of the wave flowing

out of port 2, at the port 2

plane (i.e., determine

V z− = z )

The complex ratio between V z1+( 1 =z1P ) and V z2−( 2 = z2P ) is know

as the scattering parameter S21:

j z

j z z P

j z P

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We of course could also define, say, scattering parameter S34

as the ratio between the complex values V z4+( 4 =z4P) (the wave

into port 4) and V z3−( 3 = z3P) (the wave out of port 3), given

that the input to all other ports (1,2, and 3) are zero

Thus, more generally, the ratio of the wave incident on port n to the wave emerging from port m is:

=

Note that frequently the port positions are assigned a zero

value (e.g., z1P =0, 0z2P = ) This of course simplifies the

scattering parameter calculation:

0

0 0

j m

We will generally assume that the port

locations are defined as znP = 0, and thus use

the above notation But remember where this

expression came from!

Microwave lobe

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A: Terminate all other ports with a matched load!

Q: But how do we ensure

that only one incident wave

is non-zero ?

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Note that if the ports are terminated in a matched load (i.e.,

0

L

Z = Z ), then Γ =nL 0 and therefore:

Vn+ (zn )= 0

In other words, terminating a port ensures

that there will be no signal incident on

that port!

A: Actually, both statements are correct! You must be careful

to understand the physical definitions of the plus and minus

directions—in other words, the propagation directions of waves

V + z and Vn− (zn )!

Q: Just between you and me, I think you’ve messed this up! In all

previous handouts you said that if Γ =L 0, the wave in the minus

direction would be zero:

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( ) 0 if L 0

For example, we originally analyzed this case:

In this original case, the wave incident on the load is V + ( )z

(plus direction), while the reflected wave is V − ( )z (minus

direction)

Contrast this with the case we are now considering:

For this current case, the situation is reversed The wave

incident on the load is now denoted as Vn− (zn ) (coming out of

port n), while the wave reflected off the load is now denoted as

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Perhaps we could more generally state that for some load ΓL:

z = for all ports n, the scattering parameters could be

directly written in terms of wave amplitudes V0n+ and V0−m

( )

0 0

(when 0 for all )

For each case, you must be able to

correctly identify the mathematical

statement describing the wave incident on, and reflected from, some passive load

Like most equations in engineering, the

variable names can change, but the physics described by the mathematics will not!

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One more important note—notice that for the ports terminated

in matched loads (i.e., those ports with no incident wave), the

voltage of the exiting wave is also the total voltage!

0 0

0

(for all terminated ports)

m m

j z m

−

= +

=

Thus, the value of the exiting wave at each terminated port is

likewise the value of the total voltage at those ports:

( ) 0 0

0 0

00

(for all terminated ports)

m m

VV

m mn

You might find this result helpful if attempting to determine

scattering parameters where m n≠ (e.g., S21, S43, S13), as we can

often use traditional circuit theory to easily determine the

total port voltage Vm ( )0

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However, we cannot use the expression above to determine the

scattering parameters when m n= (e.g., S11, S22, S33)

Think about this! The scattering parameters for these cases are:

0 0

n nn

n

VS

V

− +

=

Therefore, port n is a port where there actually is some

incident wave V0n+ (port n is not terminated in a matched load!) And thus, the total voltage is not simply the value of the exiting wave, as both an incident wave and exiting wave exists at port n

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Typically, it is much more difficult to determine/measure the

scattering parameters of the form Snn , as opposed to

scattering parameters of the form Smn (where m n≠ ) where

there is only an exiting wave from port m !

We can use the scattering matrix to determine the

solution for a more general circuit—one where the ports

are not terminated in matched loads!

A: Since the device is linear, we can apply superposition

The output at any port due to all the incident waves is

simply the coherent sum of the output at that port due

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This expression can be written in matrix form as:

V ,V ,V , ,V+ = ⎣⎡ + + + + ⎤⎦

The scattering matrix is a N by N matrix that completely

characterizes a linear, N-port device Effectively, the

scattering matrix describes a multi-port device the way that ΓLdescribes a single-port device (e.g., a load)!

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But beware! The values of the scattering matrix for a

particular device or network, just like ΓL, are

frequency dependent! Thus, it may be more

instructive to explicitly write:

Also realize that—also just like ΓL—the scattering matrix

is dependent on both the device/network and the Z0

value of the transmission lines connected to it

Thus, a device connected to transmission lines with

0 50

Z = Ω will have a completely different scattering

matrix than that same device connected to transmission

lines with Z0 =100Ω!!!

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02/23/07 Matched reciprocal lossless 723 1/9

Matched, Lossless, Reciprocal Devices

As we discussed earlier, a device can be lossless or reciprocal

In addition, we can likewise classify it as being matched

Let’s examine each of these three characteristics, and how

they relate to the scattering matrix

Matched

A matched device is another way of saying that the input

impedance at each port is equal to Z 0 when all other ports are terminated in matched loads As a result, the reflection

coefficient of each port is zero—no signal will be come out of a

port if a signal is incident on that port (but only that port!)

In other words, we want:

0 for all

a result that occurs when:

= 0 for all if matched

mm

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We find therefore that a matched device will exhibit a

scattering matrix where all diagonal elements are zero

For a lossless device, all of the power that delivered to each

device port must eventually find its way out!

In other words, power is not absorbed by the network—no

power to be converted to heat!

Recall the power incident on some port m is related to the

amplitude of the incident wave (V0+m) as:

2 0 0

2m

P− = Z−

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Thus, the power delivered to (absorbed by) that port is the

difference of the two:

0 0

12

N

H m

=

∑

where operator H indicates the conjugate transpose (i.e.,

Hermetian transpose) operation, so that (V+)H V+ is the inner

product (i.e., dot product, or scalar product) of complex vector

V+ with itself

Thus, we can write the total power incident on the device as:

( )

2 0

1

H N

m m

=

Similarly, we can express the total power of the waves exiting

our M-port network to be:

( )

2 0

1

H N

m m

=

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Now, recalling that the incident and exiting wave amplitudes are

related by the scattering matrix of the device:

where I is the identity matrix

Q: Is there actually some point to this long, rambling, complex

presentation?

A: Absolutely! If our M-port device is lossless then the total

power exiting the device must always be equal to the total

power incident on it

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If network is lossless, then P+ = P−

Or stated another way, the total power delivered to the device (i.e., the power absorbed by the device) must always be zero if

the device is lossless!

If network is lossless, then ∆ =P 0

Thus, we can conclude from our math that for a lossless device:

If a network is lossless, then S S IH =

Q: Huh? What exactly is this supposed to tell us?

A: A matrix that satisfies S S IH = is a special kind of

matrix known as a unitary matrix

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If a network is lossless, then its scattering matrix is S unitary

Q: How do I recognize a unitary matrix if I see one?

A: The columns of a unitary matrix form an orthonormal set!

12 22 33 4

13 23 33 43

14 22

11 21 31 41

3

2

3 44

S S S

S S

In other words, each column of the scattering matrix will have

a magnitude equal to one:

2 1

1 for all N

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Consider, for example, a lossless three-port device Say a

signal is incident on port 1, and that all other ports are

terminated The power incident on port 1 is therefore:

2 01 1

Of course, this will likewise be true if the incident wave is

placed on any of the other ports of this lossless device:

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We can state in general then that:

1

1 for all mn

=

∑

In other words, the columns of the scattering matrix must have

unit magnitude (a requirement of all unitary matrices) It is

apparent that this must be true for energy to be conserved

An example of a (unitary) scattering matrix for a lossless

device is:

Reciprocal

Recall reciprocity results when we build a passive (i.e.,

unpowered) device with simple materials

For a reciprocal network, we find that the elements of the

scattering matrix are related as:

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For example, a reciprocal device will have S21 =S12 or

where T indicates (non-conjugate) transpose

An example of a scattering matrix describing a reciprocal, but

lossy and non-matched device is:

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2/23/2007 Example A Lossless Reciprocal Network 1/4

Example: A Lossless,

Reciprocal Network

A lossless, reciprocal 3-port device has S-parameters of

11 1 2

S = , S31 =1 2, and S33 = 0 It is likewise known that all

scattering parameters are real

Æ Find the remaining 6 scattering parameters

A: Yes I have! Note I said the device was lossless and

Q: This problem is clearly

impossible—you have not provided

us with sufficient information!

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And therefore:

21 22 32 1

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These six expressions simplify to:

1221

where we have used the fact that since the elements are all

real, then S21∗ =S21 (etc.)

Q

A: Actually, we have six real equations and six real

unknowns, since scattering element has a magnitude and

phase In this case we know the values are real, and thus

the phase is either 0D or 180D (i.e., ej 0 =1 or 1

j

e π = − ); however, we do not know which one!

From the first three equations, we can find the magnitudes:

Q: I count the expressions and find 6 equations yet only a paltry 3 unknowns Your typical buffoonery appears to have led to an over-constrained condition

for which there is no solution!

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1221

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3/4/2009 MLR 3 port network 1/2

A Matched, Lossless

Reciprocal 3-Port Network

Consider a 3-port device Such a device would have a scattering matrix :

Assuming the device is passive and made of simple (isotropic)

materials, the device will be reciprocal, so that:

As a result, a lossless, reciprocal device would have a scattering

matrix of the form:

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Likewise, if we wish for this network to be lossless, the

scattering matrix must be unitary, and therefore:

2 2

real equations The problem is, the 3 complex values S21, S31 and

S32 are represented by only 6 real unknowns

We have over constrained our problem ! There are no solutions

to these equations !

As unlikely as it might seem, this means

that a matched, lossless, reciprocal

3-port device of any kind is a physical impossibility!

You can make a lossless reciprocal port device, or a matched reciprocal 3- port device, or even a matched, lossless

3-(but non-reciprocal) 3-port network

But try as you might, you cannot make a lossless, matched, and reciprocal three

port component!

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The Matched, Lossless,

Reciprocal 4-Port Network

The first solution is referred to as the symmetric solution:

Note for this symmetric solution, every row and every column of

the scattering matrix has the same four values (i.e., α, jβ, and

Guess what! I have determined

that—unlike a 3-port device—a

matched, lossless, reciprocal 4-port

device is physically possible! In fact,

I’ve found two general solutions!

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Note that for this anti-symmetric solution, two rows and two

columns have the same four values (i.e., α, β, and two zeros),

while the other two row and columns have (slightly) different

values (α, -β, and two zeros)

It is quite evident that each of these solutions are matched and

reciprocal However, to ensure that the solutions are indeed

lossless, we must place an additional constraint on the values of

α, β Recall that a necessary condition for a lossless device is:

2 1

1 for all

N mn

It is evident that if the scattering matrix is unitary (i.e.,

lossless), the values α and β cannot be independent, but must

related as:

α + β =

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Generally speaking, we will find that α ≥ β Given the

constraint on these two values, we can thus conclude that:

10

2

β

≤ ≤ and 1 1

2 ≤ α ≤

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2/23/2007 Example The Scattering Matrix 1/6

Example: The Scattering Matrix

Say we have a 3-port network that is completely characterized

at some frequency ω by the scattering matrix:

0.0 0.2 0.50.5 0.0 0.20.5 0.5 0.0

A matched load is attached to port 2, while a short circuit has

been placed at port 3:

Z0

3 0P

2 0P

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Because of the matched load at port 2 (i.e., Γ =L 0), we know

NO!! Remember, the signal V z2−( ) is incident on the matched

load, and V z2+( ) is the reflected wave from the load (i.e., V z2+( )

is incident on port 2) Therefore, V02+ = 0 is correct!

Likewise, because of the short circuit at port 3 (Γ = −L 1):

V + = −V −

You’ve made a terrible mistake!

Fortunately, I was here to

correct it for you—since Γ =L 0, the constant V02− (not V02+) is equal to zero

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Problem:

a) Find the reflection coefficient at port 1, i.e.:

01 1

01

VV

− +

Γ

b) Find the transmission coefficient from port 1 to port 2, i.e.,

02 21

01

VT

V

− +

NO!!! The above statement is not correct!

Remember, V V01− 01+ =S11 only if ports 2 and 3 are terminated in matched loads! In this problem port 3

is terminated with a short circuit

I am amused by the trivial

problems that you apparently

find so difficult I know that:

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To determine the values T21 and Γ1, we must start with the

three equations provided by the scattering matrix:

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We can divide all of these equations by V01+, resulting in:

Look what we have—5 equations and 5 unknowns! Inserting

equations 4 and 5 into equations 1 through 3, we get:

= −

=

Γ =

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Solving, we find:

( ) ( )

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