Torque Control Part 7 pptx

Torque capability and control of saturated induction motor over a wide range of flux weakening, Transaction on Industrial Electronics, Vol.. Adaptive stator flux estimator for the induc

Fig 26 Adaptive stator fluxes estimator

Fig 27 45(KW) motor behavior with the adaptive stator flux estimator

Induction Motor Vector and Direct Torque Control

It is possible to combine the two previous estimators The first one can be used for high speed, while the second estimator can be used for low speed range In this case, there is no need to program the adaptive estimator of the stator fluxes, since it will not work during the flux weakening phase

7 Conclusion

This chapter has presented a full study of the magnetic state variation of the induction motor Using a finite elements calculation program, it was possible to establish a two-phase model that takes into account the variation of the saturation level A very simple resolution method of this new model was presented The dynamic response of the new model was validated by comparing it to the dynamic response of the induction motor given by the finite element calculation program After establishing the new model it was possible to review the advanced control laws like the FOC and the DTC laws A new saturated FOC law was developed in order to enhance the dynamic behavior of the motor during the flux weakening phase, because of the difference between the motor cyclic inductances values and the values of the cyclic inductances introduced in the controllers Concerning the DTC law, it was shown that a small error in the stator resistor value will highly influence the stator flux estimation, which is done using the stator electric equation A new stator fluxes estimator was developed using rotor electric equations This estimator is less sensitive to the motor temperature variation, but it is more sensitive to the variation of the saturation level

An adaptive solution was proposed to tune the estimator parameters according to the saturation level of the motor Nevertheless the adaptive part added to the DTC algorithm, its computation time remains very small comparing to the FOC algorithm that takes into account the variation of the saturation level It is important to mention that it is possible to combine the classical estimator and the new estimator according to the speed range The classical estimator can be used at high speed, but at low speed, it is better to use the new stator flux estimator

8 References

Grotstollen, H & Wiesing, J (1995) Torque capability and control of saturated induction

motor over a wide range of flux weakening, Transaction on Industrial Electronics,

Vol 42, No 4, (August 1990) page numbers (374-381)

Vas, P & Alakula, M (1990) Field oriented control of saturated induction motors, IEEE

Transaction on Energy Conversion, Vol 5, No 1, (March 1990) page numbers (218-224), ISSN 0885-8969

Kasmieh, T & Lefevre, Y (1998) Establishment of two-phase non-linear simulation model

of the dynamic operation of the induction motor, EPJ European Physical Journal, Vol

1, No 1, (January 1998) page numbers (57-66)

Vas, P (1981) Generalized transient analysis of saturated a.c motors, Archiv fur

Elektrotechnik, Vol 64, No 1-2, (June 1981) page numbers (57-62)

Kasmieh, T (2008) Adaptive stator flux estimator for the induction motor Direct Torque

Control, Proceedings of SPEEDAM 2008, pp 1239-1241, Ischia, June 2008,

Italy

Blaschke, F (1972) The principal of field orientation as applied to the new trans-vector

closed-loop control system for rotating field machines, Siemens Review, (May

(1972)

Kasmieh, T.( 2002), Presentation of a powerful opened simulator for the saturated induction

motor traction system, Proceedings of SPEEDAM 2002, (June 2002), pp A1 24-A1 37,

Ravello, June 2002, Italy

Noguchi, T & Takahashi, I (1984) Quick torque response control of an induction motor

based on a new concept, IEEE Tech, Vol RM84-76, (September 1984) page numbers

(61-70)

Depenbrock, M & Steimel A.(1990) High power traction drives and convertors Proc of

Elect Drives Symp.’90, pp 1–9, Capri,1990, Italy

C.A, Martins.; T.A, Meynard.; X, Roboam & A.S, Carvalho2 (1999) A predictive sampling

scale model for direct torque control of the induction machine fed by multilevel

voltage-source inverters European Physical Journal-Applied Physics, AP 5, (1999)

page numbers (51-61)

5

Control of a Double Feed and Double Star Induction Machine Using Direct Torque Control

Leila Benalia

Department of electrical Engineering Batna University, Rue Chahid Med El Hadi boukhlouf

Algeria

1 Introduction

DTC is an excellent solution for general-purpose induction drives in very wide range The

short sampling time required by the TC schemes makes them suited to a very fast torque

and flux controlled drives as well the simplicity of the control algorithm DTC is inherently

a motion sensor less control method

2 Objective of the work

This chapter describes the control of doubly fed induction machine (DFIM) and the control

of doubly star asynchronous machine (DSAM), using direct torque control (DTC)

3 Principe du control direct du couple

Direct torque control is based on the flux orientation, using the instantaneous values of

voltage vector

An inverter provides eight voltage vectors, among which two are zeros (Roys & Courtine,

1995), (Carlos et al., 2005) This vector are chosen from a switching table according to the

flux and torque errors as well as the stator flux vector position In this technique, we don’t

need the rotor position in order to choose the voltage vector This particularity defines the

DTC as an adapted control technique of ac machines and is inherently a motion sensor less

control method (Casdei et al., 2001), (Kouang-kyun et al., 2000)

4 Double feed induction machine (DFIM)

In the training of high power as the rolling mill, there is a new and original solution using a

double feed induction motor (DFIM) The stator is feed by a fixed network while the rotor

by a variable supply which can be either a voltage or current source

The three phase induction motor with wound rotor is doubly fed when, as well as the stator

windings being supplied with three phase power at an angular frequencyωs, the rotor

windings are also fed with three phase power at a frequency ωrr

Under synchronous operating conditions, as shown in (Prescott & Alii., 1958), (Petersson.,

2003) , the shaft turns at an angular velocityωr, such that:

ωr=ω ωs+ rr The sign on the right hand side is (+) when the phase sequences of the three phase supplies

to the stator and rotor are in opposition and (-) when these supplies have the same phase

sequence The rotational velocity of the shaft, ωr, is expressed in electric radians per second,

to normalize the number of poles

4.1 Double feed induction machine modelling

Using the frequently adopted assumptions, like sinusoid ally distributed air-gap flux

density distribution and linear magnetic conditions and considering the stator voltages

(v sα , v sβ) and rotor voltages (v rα , v rβ ) as control inputs, the stator flux

(Φsα, Φ ), and the rotor current (sβ i rα, irβ) as state variables In the referential axis fixed in

relation to the stator, the following electrical equations are deduced:

0 0

Φ

⎡ ⎤=⎡ ⎤⎡ ⎤+ ⎡ ⎤

⎢ ⎥ ⎢ ⎥⎢ ⎥ ⎢Φ ⎥

⎣ ⎦

⎣ ⎦ ⎣ ⎦ ⎣ ⎦ (1)

ω ω

⎡ ⎤ ⎡ ⎤⎡ ⎤ ⎡ ⎤ ⎡ ⎤⎡ ⎤

⎢ ⎥ ⎢ ⎥⎢ ⎥ ⎢Φ ⎥ ⎢− ⎥⎢Φ ⎥

⎣ ⎦ ⎣ ⎦ ⎣ ⎦ ⎣ ⎦ (2) Expressions of fluxes are given by:

l I MI

l I MI

l I MI

l I MI

Φ = +

⎧

⎪Φ = +

⎪

⎨Φ = +

⎪

⎪Φ = +

⎩

(3)

The mathematical model is written as a set of equations of state, both for the electrical and

mechanical parts:

dX

X AX BU dt

•

Where:

⎥

⎥

⎥

⎥

⎥

⎦

⎤

⎢

⎢

⎢

⎢

⎢

⎣

⎡

Φ Φ

= β α β α

s s r

r I

I

X and

⎥

⎥

⎥

⎥

⎥

⎦

⎤

⎢

⎢

⎢

⎢

⎢

⎣

⎡

= β α β α

r r s s

V V V

V

The matrices A and B are given by:

Control of a Double Feed and Double Star Induction Machine Using Direct Torque Control 115

⎥

⎥

⎥

⎥

⎥

⎥

⎥

⎥

⎥

⎦

⎤

⎢

⎢

⎢

⎢

⎢

⎢

⎢

⎢

⎢

⎣

⎡

−

−

−

−

−

−

−

−

−

−

=

s s

s s

s r

s r

r s

r s

T T

M

T T

M

MT M

T

M MT

T A

1 0

0

0 1

0

1 1

1

1 1

1

' '

δ

δ ω

δ

δ δ

ω

ω δ

δ δ

δ ω

δ

(6)

B=

⎥

⎥

⎥

⎥

⎥

⎥

⎥

⎦

⎤

⎢

⎢

⎢

⎢

⎢

⎢

⎢

⎣

⎡

−

−

−

−

0 0 1

0

0 0 0

1

1 0 1

0

0 1 0

1

δ δ

δ δ

r

r

L M

L M

(7)

Jd dt

Ω

=Cem-Cr-KfΩ (8) Where J is the moment of inertia of the revolving parts, Kf is the coefficient of viscous

friction, arising from the bearings and the air flowing over the motor, and Cr is the load

couple

The equation of the electromagnetic torque is:

3

2

s

pM

The block diagram for the direct torque and flux control applied to the double feed

induction motor is shown in figure 1.The stator flux Ψref and the torque Cemref magnitudes

are compared with respective estimatedvalues and errors are processed through

hysteresis-band controllers

Stator flux controller imposes the time duration of the active voltage vectors, which move

the stator flux along the reference trajectory, and torque controller determinates the time

duration of the zero voltage vectors, which keep the motor torque in the defined-by

hysteresis tolerance band (Kouang-kyun et al.,2000), ( Xu & Cheng.,1995) Finally, in every

sampling time the voltage vector selection block chooses the inverter switching state, which

reduces the instantaneous flux and torque errors (Presada et al., 1998)

5 Simulation results machine

Figure 2 refer in order, to the variation in magnitude of the following quantities, speed, flux

and electromagnetic torque obtained while starting up the induction motor initially under

no load then connecting the nominal load During the starting up with no load the speed

reaches rapidly its reference value without overtaking, however when the nominal load is

applied a little overtaking is noticed and the command reject the disturbance The excellent

dynamic performance of torque and flux control is evident

DFIM

PARK Transformation

Estimated Stator flux

Estimated electromagnetic Torque

ref

φ

1

0

Switching

Table

cflx ccpl

_

+-Sc

Sa Sb

Uc

isa isb

β

s

i

α

s

i

α

s

β

s

i

α

s

i

β

φs α

φs

sest

φ

emest

C

1 -1

0

Network

1

2

3

4

5 6

Load

N

Fig 1 DTC applied to double feed induction machine

6 Robust control of the IP regulator

a) Speed variation

Figure 3 shows the simulation results obtained for a speed variation for the values: (Ωref =

157, 100 and 157 rad/s), with the load of 3 N.m applied at t =0.8s This results show that the

variation lead to the variation in flux and the torque The response of the system is positive,

the speed follow its reference value while the torque return to its reference value with a little

error

b) Speed reversal of rated value

The excellent dynamic performance of torque control is evident in figure 4, which shows

torque reversal for speed reversal of (157, -157 rad/s), with a load of 5N.m applied at t=1 s

The speed and torque response follow perfectly their reference values with the same

response time The reversal speed leads to a delay in the speed response, to a peak

oscillation the current as well as a fall in the flux magnitude which stabilise at its reference

value

Control of a Double Feed and Double Star Induction Machine Using Direct Torque Control 117

Electromagnetic to

Time (s) Time (s)

Time (s)

Fig 2 Simulation results obtained with an IP regulator

Time (s)

Electromagnetic to

Time (s)

Time (s)

Fig 3 Robust control for a speed variation

Time (s)

Electromagnetic to

Time (s)

Time (s)

Fig 4 Robust control under reversal speed

c) Robust control for load variation

The simulation results obtained for a load variation (Cr = 3 N.m, 6 N.m) in figure 5, show

that the speed, the torque and the flux are inflated with this variation Indeed the torque and

the speed follow their reference values

Time (s)

Electromagnetic to

Time (s)

Time (s)

Fig 5 Robust control under load variation

Control of a Double Feed and Double Star Induction Machine Using Direct Torque Control 119 d) Robust control of the regulator under stator resistance variation

In order to verified the robustess of the regulator under motor parameters variations we carried out a test for a variation of 50% in the value of stator resistance at tile t= 1.5s The speed is fixed at 157 rad/s and a resistant torque of 5 N.m is applied at t= 1s Figure 6 shows the in order the torque response, the current, the stator flux and the speed The results indicate that the regulator is very sensitive to the resistance change which results in the influence on the torque and the stator flux

Time (s)

Electromagnetic to

Time (s)

Time (s)

Fig 6 Robust control under stator resistance variation

7 Double star induction machine (DSIM)

For the last 20 years the induction machines with a double star have been used in many applications for their performances in the power fields because of their reduced pulsation when the torque is minimum (Kalantari et al.,2002).The double stator induction machine needs a double three phase supply which has many advantages It minimise the torque pulsations and uses a power electronics components which allow a higher commutation frequency compared to the simple machines However the double stator induction machines supplied by a source inverter generate harmonic which results in supplementary losses (Hadiouche et al., 2000) The double star induction machine is not a simple system, because

a number of complicated phenomena’s appears in its function, as saturation and skin effects (Hadiouche et al., 2000)

The double star induction machine is based on the principle of a double stators displaced by α=300 and rotor at the same time The stators are similar to the stator of a simple induction machine and fed with a 3 phase alternating current and provide a rotating flux

Each star is composed by three identical windings with their axes spaced by 2π/3 in the space Therefore, the orthogonality created between the two oriented fluxes, which must be

strictly observed, leads to generate decoupled control with an optimal torque (Petersson.,

2003)

This is a maintenance free machine

The machine studied is represented with two stars windings: As1Bs1Cs1 et As2Bs2Cs2 which

are displaced by α=30° and thee rotorical phases: Ar Br Cr

Star N°1

Star N°2

Cr

Bs1

α

θ

As1 As2

Ar

Br

Cs1

C

Rotor

Bs2

Fig 7 Double star winding representation

8 Double star induction machine modeling

The mathematical model is written as a set of state equations, both for the electrical and

mechanical parts:

[ ] [ ] [ ]

abc s s abc s abc s abc s s abc s abc s abc r r abc r abc r

d

dt d

dt d

dt

⎡ ⎤= ⎡ ⎤+ ⎡Φ ⎤

⎣ ⎦ ⎣ ⎦ ⎣ ⎦

⎡ ⎤= ⎡ ⎤+ ⎡Φ ⎤

⎣ ⎦ ⎣ ⎦ ⎣ ⎦

⎡ ⎤= ⎡ ⎤+ ⎡Φ ⎤

⎣ ⎦ ⎣ ⎦ ⎣ ⎦

(1)

Jd dt

Ω

=Cem-Cr-Kf Ω (2) Where:

J is the moment of inertia of the revolving parts

Kf is the coefficient of viscous friction, arising from the bearings and the air flowing over the

motor

Cem is the electromagnetic torque

The electrical state variables are the flux, transformed into vector [ Φ ] by the “dq”

transform, while the input are the “dq” transforms of the voltages, in vector [V]

[ ] [ ] [ ] [ ] [ ] B v